figure 1. that 1510 / 1512 equivalent circuit diagram ( that 1512 values shown in p arentheses ) 12 15 8 8 rg2 11 13 7 7 v+ 9 11 6 6 out 10 10 5 5 ref 6 7 4 4 v- 5 5 3 3 +in 4 4 2 2 -in 3 2 1 1 rg1 so14 pkg so16 pkg so8 pkg dip8 pkg pin name table 1. pin assignments features ? low noise: 1 nv/ hz input noise (60db gain) 34 nv/ hz input noise (0db gain) (1512) ? low thd+n (full audio bandwidth): 0.001% 40 db gain 0.005% @ 60 db gain ? low current: 6ma typ. ? wide bandwidth: 7mhz @ g=100 ? high slew rate: 19 v/ s ? wide output swing: 13.3v on 15v supplies ? gain adjustable from 0 to >60 db with one external resistor ? industry standard pinouts applications ? differential low noise preamplifiers ? differential summing amplifiers ? differential variable gain amplifiers ? microphone preamplifiers ? moving-coil transducer amplifiers ? line input stages ? audio ? sonar ? instrumentation that 1510, 1512 the that 1510 and 1512 are high perform- ance audio preamplifiers suitable for microphone preamp and bus summing applications. the ics are available in a variety of packages and pin configurations, making th em pin compatible with the analog devices ssm2019 and ssm2017 (discontinued), and the texas instruments ina217 and ina163. gain for both parts is adjustable via one external resistor, making it possible to control gain over a wide range with a single-gang potenti- ometer. the 1510 gain equation is identical to that of the ssm 2019, reaching 6 db gain with a 10 k ? resistor. the 1512 reaches 0 db gain with a 10 k ? resistor. because the 1512 exhibits significantly lower noise at lower gain settings, it is recommended over the 1510 for new designs. designed from the ground up in that?s complementary dielectric isolation process and including laser-trimmed si-chrome thin film resistors, the that 1510 and 1512 improve on existing integrated microphone preamps by offer- ing lower noise at low gains, wider bandwidth, higher slew rate, lower distortion, and lower supply current. the parts feature internal esd overload protection on all critical pins. in short, the that 1510 and 1512 provide superior performance in a popular format at an affordable price. description low-noise, high performance audio preamplifier ic that corporation; 45 sumner street; milford, ma 01757-1656; us a tel: +1 508 478 9200; fax: +1 508 478 0990; web: www.thatcorp.com copyright ? 2013, that corporation. document 600031 rev 08 v+ v- -in r g2 r g1 +in out ref + - 5k 5k (10k) 5k 5k (10k) 5k 5k output stage input stage r a r b -a v -a v table 2. ordering information 1512s14-u inquire 1512s08-u 1512p08-u 1512 1510s14-u 1510w16-u 1510s08-u 1510p08-u 1510 so14 pkg so16 pkg so8 pkg dip8 pkg part type
document 600031 rev 08 page 2 of 8 that 1510/1512 low-noise high performance audio preamplifier ic that corporation; 45 sumner street; milford, ma 01757-1656; us a tel: +1 508 478 9200; fax: +1 508 478 0990; web: www.thatcorp.com copyright ? 2013, that corporation positive supply voltage (v cc ) +20 v negative supply voltage (v ee ) -20 v input voltage (v in max )v cc + 0.5v, v ee - 0.5v output short-circuit duration (t sh ) continuous lead temp. (t lead ) (soldering 10 sec) 260 c operating temperature range (t op ) -40 to +85c storage temperature range (t st ) -40 to +125c junction temperature (t j ) 150c absolute maximum ratings 2,3 specifications 1 1510 1512 parameter symbol conditions min typ max min typ max units supply current i cc , -i ee no signal ? 6.0 7.9 ? 6.0 7.9 ma v cc = -v ee = 20v ? ? 8.0 ? ? 8.0 ma input bias current i b no signal; either input ? 4.8 14 ? 4.8 14 a connected to gnd input offset current i b-off no signal -1.4 ? +1.4 -1.4 ? +1.4 a offset voltage output stage output offset vos oo no signal, v cm =0 -5 ? +5 -5 ? +5 mv input stage input offset vos ii -250 ? +250 -250 ? +250 v total output offset g=voltage gain -5-0.25g 5+0.25g -5-0.25g 5+0.25g mv input voltage range common mode v in-cm common mode, all gains ? 13 ? ? 13 ? v differential mode v in-unbal unbalanced -13 ? +13 -13 ? +13 v one input to gnd, 0db gain differential gain g diff 0 ? 70 -6 ? 64 db ref input voltage range ? 8 ? ? 8 ? v ref input impedance ? 10 ? ? 15 ? k ? ref input gain to output ? 0 ? ? 0 ? db input impedance z in-diff differential 0db gain ? 32||1.9 ? ? 37||1.9 ? m ? ||pf 20db gain ? 32||2.0 ? ? 37||2.0 ? m ? ||pf 40db gain ? 32||2.5 ? ? 36||3.1 ? m ? ||pf 60db gain ? 29||8.0 ? ? 31||13.9 ? m ? ||pf z in-cm common mode all gains ? 8||7.7 ? ? 9||7.7 ? m ? ||pf electrical characteristics 2 1. all specifications are subject to change without notice. 2. unless otherwise noted, t a =25oc, v cc =+15v, v ee = -15v. 3. stresses above those listed under ?absolute maximum ratings? may cause permanent damage to the device. these are stress ra tings only; the functional operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not impl i ed. exposure to absolute maximum rating conditions for extended periods may affect device reliability. parameter symbol conditions min typ max units positive supply voltage v cc +5 +20 v negative supply voltage v ee -5 -20 v recommended operating conditions
that 1510/1512 low-noise page 3 of 8 document 600031 rev 08 high performance audio preamplifier that corporation; 45 sumner street; milford, ma 01757-1656; us a tel: +1 508 478 9200; fax: +1 508 478 0990; web: www.thatcorp.com copyright ? 2013, that corporation 1510 1512 parameter symbol conditions min typ max min typ max units common mode rejection cmr v cm = 10v; dc to 60 hz 0 db gain 45 60 ? 45 60 ? db 20 db gain 65 80 ? 65 80 ? db 40 db gain 85 100 ? 85 100 ? db 60 db gain 105 120 ? 105 120 ? db power supply rejection psr v cc = -v ee ; 5v to 20v; dc to 60 hz 0 db gain ? 85 ? ? 60 ? db 20 db gain ? 105 ? ? 105 ? db 40 db gain ? 120 ? ? 120 ? db 60 db gain ? 124 ? ? 124 ? db total harmonic distortion thd+n v out = 7vrms; r l = 5 k ? f = 1khz; bw = 20 khz 0 db gain ? 0.0005 ? ? 0.001 ? % 20 db gain ? 0.0012 ? ? 0.004 ? % 40 db gain ? 0.0016 ? ? 0.005 ? % 60 db gain ? 0.005 ? ? 0.008 ? % equivalent input noise e n(in) f = 1khz, 0 db gain ? 57 ? ? 34 ? nv/ hz 20 db gain ? 7 ? ? 4.6 ? nv/ hz 40 db gain ? 1.7 ? ? 1.4 ? nv/ hz 60 db gain ? 1 ? ? 1 nv/ hz input current noise i n(in) 60 db gain ? 2.0 ? ? 2.0 ? pa/ hz noise figure nf 60 db gain r s = 150 ? ? 1.6 ? ? 1.6 ? db r s = 200 ? ? 1.3 ? ? 1.3 ? db slew rate sr r l = 2 k ? c l = 50 pf 13 19 ? 13 19 ? v/s bandwidth -3db bw -3db r l = 2 k ? ; c l = 10 pf 0 db gain ? 15 ? ? 11 ? mhz 20 db gain ? 8 ? ? 9 ? mhz 40 db gain ? 7 ? ? 7 ? mhz 60 db gain ? 3 ? ? 1.6 mhz output gain error g er (out) f = 1khz; r l = 2 k ? r g =infinite, g=0 db -0.5 ? +0.5 ? ? ? db r g = 1.1 k ? , g=20 db -0.5 ? +0.5 ? ? ? db r g = 101 ? , g=40 db -0.5 ? +0.5 ? ? ? db r g = 10 ? , g=60 db -0.5 ? +0.5 ? ? ? db r g = 10 k ? , g=0 db ? ? ? -0.5 ? +0.5 db r g = 526.3 ? , g=20 db ? ? ? -0.5 ? +0.5 db r g = 50.3 ? , g=40 db ? ? ? -0.5 ? +0.5 db r g = 5 ? , g=60 db ? ? ? -0.5 ? +0.5 db output voltage swing v o r l = 2 k ? all gains 13 13.3 ? 13 13.3 ? v output short circuit current i sc r l = 0 ? ? 17 ? ? 17 ? ma minimum resistive load r lmin 2?? 2?? k ? maximum capacitive load c lmax ? ? 300 ? ? 300 pf gain equation a v = 1 + 10 k
r g a v = 0.5 + 5 k
r g electrical characteristics (con?t) 2
gain setting a single external resistor (r g ) between the r g1 and r g2 pins is all that is needed to set the gain of the that 1510/1512, according to the formulae: for the 1510: or a v = 1 + 10 k
r g for the 1512: where a v = 0.5 + 5 k
r g a v is the voltage gain of the part. either part may reach unity gain, but the value of r g required varies significantly between the two parts. for the 1510, gain is 0db when r g is infinite (open); this is the minimum gain for the 1510. at infinite r g , the 1512 reaches -6db gain; this is the minimum gain for the 1512. with r g =10k ? , the 1512 reaches 0db gain. overall gain accuracy depends on the tolerance of r g and the accuracy of the internal thin-film resis- tors connected to pins r g1 and r g2 in the 1510/1512 (r a & r b in figure 1). these internal resistors have a typical initial accuracy (a t room temperature) of 0.5%, and are typically stable with temperature to within 100 ppm/c. gain will drift with tempera- ture based on the mismatch between the temperature coefficient of the external r g and that of the internal resistors r a & r b . for variable-gain applications where gain accuracy is important, that recommends using discrete, switched resistors for r g . where continuous control is required, or where gain accuracy is less critical, a potentiometer may be used. in such appli- cations, designers should take care in specifying the element construction to avoid excess noise. the potentiometer taper will set the circuit?s characteris- tic of gain vs. pot rotation. typically, reverse log (reverse audio) taper elements offer the desired behavior in which gain increases with clockwise rotation (and lower values for r g ). see that design note 138 for a discussion of potentiometer taper and gain for the 1510 and 1512 compared to similar parts from other manufacturers. noise performance both parts exhibit excellent voltage noise performance of ~1 nv/ hz at high gains. with ~2 pa/ hz current noise, they are optimized for relatively low source impedance applications, such as dynamic microphones with typically a few hundred ohm output impedances. but, because they have different internal gain structures, the 1510 has higher equivalent input noise at 0db gain (~57 nv/ hz) than the 1512, which runs 4.5 db lower at ~34 nv/ hz. the unusual and superior topology of the that 1512 makes its noise perform- ance comparable to some of the better discrete designs currently available. inputs simple configurations as shown in figure 2, the 1510/1512 includes protection diodes at all pins except v+ and v-. document 600031 rev 08 page 4 of 8 that 1510/1512 low-noise high performance audio preamplifier ic that corporation; 45 sumner street; milford, ma 01757-1656; us a tel: +1 508 478 9200; fax: +1 508 478 0990; web: www.thatcorp.com copyright ? 2013, that corporation v+ v- -in r g2 r g1 +in out ref + - 5k 5k (10k) 5k 5k (10k) 5k 5k output stage input stage r a r b -a v -a v figure 2. that 1510 / 1512 equivalent circuit with protection diodes applications
these diodes reduce the likelihood that accidental electrostatic discharge (esd) or electrical over stress (eos) will damage the ics. other diodes across the base-emitter junctions of the input transistors prevent excessive reverse biasing of these junctions (which would degrade the noise performance of the input devices). other than the protection diodes, the 1510/1512 input pins are connected only to the bases of their respective input devices. for proper operation, the bases must be provided a source of dc bias that will maintain the inputs within the ic's input common- mode range. figure 3 shows the simplest approach; dc bias is supplied via r 1 and r 2 . at 1 k ? each, they will minimize pickup of unwanted noise and interfer- ence, as well as generate relatively little noise due to input current noise in the 1510/1512. however, at high gains, their inherent voltage noise, plus the 1510/1512's input current noise drawn across these resistors, adds significantly to the noise at the 1510/1512's output. because r g is dc coupled in the circuit of figure 3, the dc level at the output of the 1510/1512 will vary with gain. in most applications, the output should be ac-coupled to the next stage. for applica- tions where r g is variable (via a pot or switched resistors) to allow gain adjustment, r g should be ac-coupled as shown in figure 4. by adding c g in series with r g , dc gain is fixed (at unity for the 1510, and ? for the 1512). this constrains the output dc offset to just over +/-5 mv, and prevents it from varying with gain. with this low offset, ac coupling of the output is usually unnecessary. c g must be large enough not to interfere with low-frequency response at the smallest values of r g . for 60 db gain, r g =10 ? (1510) or r g =5 ? (1512). for a -3 db point of approximately 5 hz, c g =3,300 f (1510), or c g =6,800 f (1512). for other maximum gains or minimum frequencies, scale c g accordingly. phantom power phantom power is required for many condenser microphones. that recommends the circuit of figure 5 when phantom power is included 4 . r 3 , r 4 , and d 1 - d 6 are used to limit the current that flows through the 1510/1512 inputs when the circuit inputs (-in and +in) are shorted to ground while phantom power is turned on. this causes c 4 and/or c 5 to discharge through other circuit components, often generating transient currents of several amps. r 3 and r 4 should be at least 10 ? to limit destructive that 1510/1512 low-noise page 5 of 8 document 600031 rev 08 high performance audio preamplifier that corporation; 45 sumner street; milford, ma 01757-1656; us a tel: +1 508 478 9200; fax: +1 508 478 0990; web: www.thatcorp.com copyright ? 2013, that corporation rg +in out -in rg2 rg1 u1 that 1510/1512 -15 +15 -in +in r1 1k r2 1k c1 470p c2 470p c3 47p out c6 100n c9 100n v+ v- ref figure 3. basic 1510 / 1512 circuit 4. in revisions 0 and 1 of this data sheet, we recommended using schottky diodes (1n5819 types) at d 1 ~ d 4 to protect the 1510/1512 inputs against overloads. subse - quently, we discovered that the leakage of these diodes could cause problems with dc fluctuations (hence noise) at the 1510/151 2 output. upon further investigation, we concluded that conventional rectifier diodes like the 1n4004 (the glass-passivated gp version) provide adequate protection and d o not introduce unacceptable leakage. additionally, 1n4004 diodes are much cheaper and more readily available than the schottky types. since publishing revision 4, we determined that the internal reverse-bias diodes between the pins +in/r g2 and -in/r g1 may be damaged by phantom power faults under certain conditions. small-signal diodes (d 5 and d 6 ) avoid this problem by appearing in parallel with the internal diodes, diverting excess current around the 1510/1512.
currents. (hi g her values further limit current flow, but introduce additional source impedance and noise.) d 1 through d 4 prevent the ic?s inputs from significantly exceeding the supply rails. d 5 and d 6 steer currents around the input stage in the 1510/1512, preventing damage. the series combination of c 4 and c 5 should be made large to minimize hig h-pass filtering of the signal based upon the sum of the values of r 1 +r 2 . as well, keeping their reactance low relative to the exter- nal microphone's source impedance will avoid increasing the effects of low-frequency current noise in the 1510/1512 input stage. other manufacturers have recommended, and many pro audio products include, a zener diode arrangement connected to the bridge rectifier instead of the connection to v+ and v- as shown in figure 5. that does not recommend this approach, because we find that r 3 and r 4 must be made much larger (e.g., 51 ? ) in order to limit peak currents enough to protect reasonably sized zener diodes (eg. 1/2 w). such large series input resistors will limit the noise performance of the preamp. the ultimate floor is set by the impedance of the microphone, but any additional series resistance further degrades performance. for further insights into this subject, see the audio engineering society preprints "the 48 volt phantom menace," by gary k. hebert and frank w. thomas, presented at the 110th a es convention and ?the 48 volt phantom mena ce returns?, by rosal- fonso bortoni and wayne kirkwood presented at the 127th aes convention. impedance and line input configurations a higher common-mode input impedance is desirable (compared with that of figures 3 and 4) when input coupling capacitors (c 4 and c 5 ) are used to block phantom power. at low frequencies where the reactance of c 4 and c 5 become significant (compared to the common-mode input impedances), the two capacitors interact with the common-mode input impedance (seen looking to the right-side of both capacitors) to form voltage dividers for common-mode signals. differences in the two capaci- tors' values leads to different voltage dividers, spoil- ing the low-frequency commo n-mode rejection of the stage. since c 4 and c 5 are generally large, electrolytic types, precise matching is difficult and expensive to achieve. high common-mode input impedance reduces the matching requirement by decreasing the frequency at which the capacitive reactance becomes significant inversely with the common-mode input impedance. the "t-bias" circuit (r 1 , r 2 , and r 7 ) shown in figure 5 accommodates this objective. in this circuit, r 1 and r 2 are connected to a third resistor r 7 , boost- ing the low-frequency common mode input document 600031 rev 08 page 6 of 8 that 1510/1512 low-noise high performance audio preamplifier ic that corporation; 45 sumner street; milford, ma 01757-1656; us a tel: +1 508 478 9200; fax: +1 508 478 0990; web: www.thatcorp.com copyright ? 2013, that corporation rg cg +in out -in rg2 rg1 u1 that 1510/1512 -1 5 +15 -in +in r1 1k r2 1k c1 470p c2 470p c3 47p out c6 100n c9 100n v+ v- ref figure 4. basic 1510 / 1512 circuit with variable gain
impedance (as "seen lookin g in" from the couplin g capacitors) to the value of r 1 + (2*r 7 ) -- approxi- mately 45 k ? with the values shown. the increased common mode impedance from t-bias improves lf common mode rejection by reducing capacitor matching requirements by mo re than a factor of ten over the simpler circuit wherein r 7 =0 ? . the circuit works well with the values shown. note also that the overall common-mode input impedance of the circuit is dominated by the phantom-power resistors (r 5 and r 6 ). for the circuit of figure 5, this is approximately 5.9 k ? per leg. the 1510/1512 can be used as a line input receiver by adding attenuation to the preamplifier inputs and changing the circuit topology to allow switchin g of input, fixed attenuation, and g ain adjus t - ment. the optimum circuit depends on the specific requirements of the application. for more details and specific applications advice, please consult that's application notes, or our applications engineers at the address and telephone below or via email at apps_support@thatcorp.com. reference terminal the "ref" pin provides a reference for the output signal, and is normally connected to analog ground. if necessary, the "ref" pin can be used for offset correction or dc level shif ting. however, in order to prevent spoiling the excellent common-mode rejec- tion of the 1510/1512, the source impedance driving the ?ref? pin should be under 1 ? . that 1510/1512 low-noise page 7 of 8 document 600031 rev 08 high performance audio preamplifier that corporation; 45 sumner street; milford, ma 01757-1656; us a tel: +1 508 478 9200; fax: +1 508 478 0990; web: www.thatcorp.com copyright ? 2013, that corporation figure 5. recommended 1510 / 1512 circuit with phantom power rg +in out -in rg2 rg1 u1 that 1510/1512 -in +in r1 1k2 r2 1k2 r7 22k c1 470p c2 470p c3 47p out c4 22u c5 22u d3 1n4004gp d4 1n4004gp d1 1n4004gp d5 1n4148 d6 1n4148 d2 1n4004gp +15 -15 r6 6k8 r5 6k8 +48v r3 r4 10 -15 +15 c6 100n c9 100n ref v+ v- 10 cg on package information both the that 1510 and 1512 are available in 8-pin soic, 8-pin dip, and 14-pin soic packages. the 1510 is also available in a 16-pin (widebody) soic package. other version/package combinations will be considered based on customer demand. the package dimensions are shown in figures 6, 7, 8, & 9, while pinouts are given in table 1. all versions of the 1510 and 1512 are lead free and rohs compliant. material declaration data sheets on the parts are available at our web site, www.thatcorp.com or upon request.
document 600031 rev 08 page 8 of 8 that 1510/1512 low-noise high performance audio preamplifier ic that corporation; 45 sumner street; milford, ma 01757-1656; us a tel: +1 508 478 9200; fax: +1 508 478 0990; web: www.thatcorp.com copyright ? 2013, that corporation b a k f h e d g j c item a b c d e f g h j k 1 millimeters 9.520.10 6.350.10 7.49/8.13 0.46 2.54 3.68/4.32 0.25 3.180.10 8.13/9.40 3.300.10 inches 0.3750.004 0.2500.004 0.295/0.320 0.018 0.100 0.145/0.170 0.010 0.1250.004 0.320/0.370 0.1300.004 figure 6. 8-pin dip package outline figure 7. 16-pin so wide package outline 0.41/1.27 h 0.016/0.05 0.228/0.244 0.0075/0.0098 0.053/0.068 0.014/0.018 0.189/0.196 inches 0.150/0.157 g h f c b d f g d e a b c item millimeters 0.36/0.46 0.19/0.25 1.35/1.73 1.27 4.80/4.98 3.81/3.99 5.80/6.20 0.050 a e figure 8. 8-pin soic package outline figure 9. 14-pin soic package outline e c b d a h f g 1 0.41/1.27 h 0.016/0.05 0.228/0.244 0.0075/0.0098 0.053/0.068 0.014/0.018 0.337/0.346 inches 0.150/0.157 f g d e a b c item millimeters 0.36/0.46 0.19/0.25 1.35/1.73 1.27 8.56/8.79 3.81/3.99 5.80/6.20 0.050 revision history 3 corrected typographical error in specification table. 10/02/13 2829 08 2 added max. input voltage specification. 9/16/09 2322 07 page changes date eco revision
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